Series switch bridgeless power supply

ABSTRACT

A series-switch bridgeless power supply provides common-mode EMI filtering. The power supply includes a center-tapped inductive device bifurcated into first and second windings. The AC input, provided at first and second input terminals, is applied to the center-tap of the inductive device. First and second switches are connected to distal ends of the first and second windings, respectively, and are connected in series with one another to form a circuit path from the first input terminal, through the inductive device and each of the series-connected switches, back through the inductive device and to the second input terminal. A controller turns the switches On and Off to modulate the current through the inductive device. Common-mode voltage generated by the modulation of the first and second switches is filtered by connection of each switch to a junction defined between a pair of capacitors connected in series between the first and second input terminal. The topology provides a first stage, two-pole filter for filtering common-mode voltages.

BACKGROUND

The present invention relates to power supplies and in particular topower factor correction (PFC) power supplies.

Electric power is distributed almost universally in an alternatingcurrent (AC) format that allows for efficient transmission. Most deviceshowever, including personal computers, televisions, etc., require directcurrent (DC) power. Power supplies (or converters) act to convert the ACinput supplied by a line to a DC output suitable for consumption by adevice or load, or act to convert a DC input to a DC output (i.e., aDC-to-DC converter). A switched-mode power supply (SMPS) employing aboost regulator is commonly employed in this role of AC-to-DC orDC-to-DC power conversion. A benefit of employing a SMPS having a boostregulator topology is the boost regulator can be controlled to providepower factor correction, wherein the term “power factor correction”refers to the efficiency of the circuit (i.e., real power versusapparent power). Power factor correction typically involves ensuringthat the current drawn by the PFC circuit is in-phase with the voltageprovided by the PFC boost regulator. Subsequent stages may be employedto step-down the output of the PFC boost regulator to a desired DCoutput voltage, and other topologies may be employed in conjunction withor instead of boost regulator topologies, such as flyback topologies.

A distinction between PFC power supplies can be made between those powersupplies that include a first stage rectifier bridge and so-calledbridgeless PFC boost regulators. The first stage rectifier bridgeincludes four diodes, connected in a bridge topology to rectify the ACinput supplied by the line. The voltage drops associated with each dioderepresent losses that lower the overall efficiency of the power supply.Improvements to PFC power supplies have included the use of half-bridgedesigns that employ two diodes instead of four, and bridgeless PFC powersupplies that further reduce the number of semiconductor devices (e.g.,diodes, switches) required in any given circuit path, thereby furtherimproving efficiency. However, typical bridgeless PFC power supplytopologies introduce common-mode electromagnetic interference (EMI) thatis difficult to filter.

SUMMARY

A series-switch bridgeless power supply converts an AC input to a DCoutput. The power supply includes first and second terminals connectedto receive the AC input. The power supply further includes first andsecond capacitors connected in series with one another between the firstand second terminals, with a first junction defined between the firstand second capacitor. The power supply includes a center-tappedinductive device having a primary winding bifurcated into a firstwinding and a second winding. The first winding has a first end and asecond end, with the first end connected to the first terminal. Thesecond winding has a first end and a second end, with the first endconnected to the second terminal. A capacitor is connected between thefirst end of the first winding and the first end of the second winding.The power supply includes first and second switches, each switch havinga control terminal and first and second controlled terminals. The firstcontrolled terminal of the first switch is connected to the second endof the first winding, and the first controlled terminal of the secondswitch is connected to the second end of the second winding. The secondcontrolled terminals of the first and second switches are electricallyto one another, such that the first and second switches are connected inseries with one another. A controller is connected to the controlterminals of the first and second switches, and selectively turns theswitches On and Off to charge/discharge the inductive device. Filteringof common-mode voltage is provided by connecting the second controlledterminals of the first and second switches to the junction between thefirst and second capacitors.

BRIEF DESCRIPTION OF THE DRAWINGS

FIGS. 1A and 1B are circuit diagrams of a bridgeless PFC flybackconverter power supply according to an embodiment of the presentinvention.

FIG. 2 is a circuit diagram of a bridgeless PFC boost regulator powersupply according to an embodiment of the present invention.

DETAILED DESCRIPTION

The power supply topology taught by the present invention reduces commonmode electromagnetic interference (EMI) that is commonly found inbridgeless PFC power supplies. The topology relies on a center-tappedinductive device (e.g., a center-tapped transformer in a flybackconfiguration, center-tapped inductor in a boost regulatorconfiguration). Switching devices having first controlled ends (e.g.,sources of a MOSFET) are connected to opposite ends of the center-fedinductive device and second controlled ends (e.g., drains of eachMOSFET) are connected to one another such that the switches areconnected in series with one another during both cycles of the AC input.A pair of capacitors are connected across the AC inputs and the junctionbetween the pair of capacitors is connected to a common (i.e., ground)node, which is also connected to the second controlled ends of eachswitch. This topology allows common-mode EMI to be shunted from thejunction between the pair of capacitors to the second controlled ends ofthe respective switches.

FIGS. 1A and 1B are circuit diagrams of bridgeless PFC flyback converterpower supply 10 (hereinafter, “power supply 10”) according to anembodiment of the present invention. Power supply 10 converts the ACinput received at input terminals P and N to a DC output Vo. The ACinput includes a positive half-cycle and a negative half-cycle. Tosimplify the discussion of the circuit topology the voltages aredescribed relative to the common node, assumed to be approximately zero.As a result, during the positive half-cycle the voltage at inputterminal P is described as positive, and during the negative half-cyclethe voltage at input terminal N is described as positive.

The embodiment shown in FIGS. 1A and 1B is a series-switch bridgelessflyback supply 10 with central-fed transformer T1. Power supply 10 isdescribed as bridgeless because it does not include a rectifier bridgecommonly employed in supply circuits to rectify the AC input voltage.Rather, input terminal P is connected via inductors L1 a, L2 a to afirst center-tap position within the primary winding of transformer T1.Input terminal N is connected via inductors L1 b, L2 b to a secondcenter-tap position within the primary winding of transformer T1. Inthis way, the primary winding of transformer T1 is bifurcated into afirst and second winding, and is center-fed by the connection of the ACinputs to the center-tap position. Capacitors C1, C2 are connected inseries with one another between the AC input terminals and the junctionbetween capacitors C1, C2 provides a connection to a common node,discussed in more detail below.

The ends of the primary winding of transformer T1 are connected torespective switches Q1 and Q2, which include first and second controlledterminals and a control terminal. In the embodiment shown in FIGS. 1Aand 1B, switches Q1 and Q2 are metal-oxide semiconductor field-effecttransistors (MOSFETs), each having a drain, a source and a gate thatcorrespond to first and second controlled terminals and the controlterminal, respectively. In other embodiments, other switching devicessuch as bipolar junction transistors (BJTs), insulated gate BJTs, etc.,may be employed by power supply 10. In the embodiment shown in FIGS. 1A,1B, the drains of switches Q1, Q2 are connected to the respective endsof the primary winding of transformer T1. Controller 12 provides drivesignals to the gates of switches Q1, Q2 to control whether the switchesare On (conducting) or Off (not conducting). The sources of switches Q1,Q2 are connected together (via sense resistors Rsense1, Rsense2), withthe junction between the current sense resistors being connected to acommon node.

During operation as a flyback converter, switches Q1 and Q2 are turnedOn and Off to transfer energy from the primary winding to the secondarywinding of transformer T1. Because the sources of switches Q1 and Q2 areconnected together, a circuit path is created in which switches Q1 andQ2 are connected in series. Depending on the polarity of the AC input,one switch operates as a high-frequency switch to modulate the AC inputvoltage while the other switch operates as a synchronous rectifier dueto the presence of a body diode between the source and drains of eachswitch. This is illustrated in more detail with respect to the currentpaths and waveforms generated during the positive and negativehalf-cycles of the AC input voltage. Diodes D1 and D2 are connected tothe secondary winding and rectify the output of the secondary winding toprovide a DC output across capacitor C6.

A benefit of this circuit topology is the ability of the circuit tofilter common-mode EMI that would otherwise be provided across capacitorC3. Typical methods of filtering this common-mode EMI include thepresence of large inductive filters connected to each AC input. However,by connecting the sources of switches Q1, Q2 to the junction betweencapacitors C1, C2, a two-pole filter is created that is capable ofshunting common-mode EMI (harmlessly) through capacitor C1 or C2 to thesources of switches Q1, Q2. The operation of power supply 10 infiltering common-mode EMI is described below with respect to both thepositive and negative half-cycles of the AC input voltage.

FIG. 1A depicts the flow of current through power supply 10 during thepositive half-cycle of the AC input voltage VAC and FIG. 1B depicts theflow of current through power supply 10 during the negative half-cycleof AC input VAC. The flow of current is depicted by the direction of thearrows. In addition, sample waveforms are illustrated in FIGS. 1A, 1Bwith respect to several portions of the circuit, illustrating thedesired filtering of common-mode voltages.

In the positive half-cycle shown in FIG. 1A, the voltage at terminal Pis positive relative to the voltage at terminal N. As a result, acurrent path is created that flows (as indicated by the arrows) frominput terminal P, through inductors L1 a, L2 a to the center-tap on theprimary winding of transformer T1, through switch Q1, current senseresistors Rsense1, Rsense2, and series-connected switch Q2, to thecenter-tap on the primary winding of transformer T1, and back to inputterminal N via inductors L2 b, L1 b. During this time, controller 12turns switch Q1 On and Off to generate the desired DC output and providethe desired power factor correction to the AC input. When switch Q1 isOn, current flows through the described circuit path, and when switch Q1is Off the circuit path is broken and no current flows in the circuit(although when switch Q1 is Off, flyback current is generated in thesecondary winding of transformer T1).

The modulation of switch Q1 is illustrated by voltage waveform 20 shownadjacent to switch Q1, with the positive half-cycle being modulated asindicated into a plurality of pulses. The modulation of switch Q1results in significant common-mode voltages being provided onto thecenter-tap of transformer T1 as common-mode EMI, illustrated by voltagewaveform 18 shown adjacent to the nodes on either side of capacitor C3.The series-connection of switch Q2 (acting as a synchronous rectifier)prevents common-mode EMI from being propagated across switch Q2, asillustrated by voltage waveform 16 shown adjacent to switch Q2. Tofilter the common-mode voltage (EMI) provided at the center-tap oftransformer T1, a two-pole filter is created by connecting the sourcesof switches Q1, Q2 to the junction between capacitors C1, C2. Thelow-resistance path created by switch Q2 between the common node and theAC input terminal N, and the connection of the common node to thejunction between capacitors C1, C2, results in the voltage between theinput terminal and the junction between the capacitors being very small.As a result, common-mode EMI is shunted from the junction of capacitorsC1,C2 to the source of switch Q1

In the negative half-cycle shown in FIG. 1B, the input voltage atterminal N is positive relative to the voltage at terminal P, andcurrent flows (as indicated by the arrows) from the terminal N, throughinductors L1 b, L2 b to the center-tap on the primary winding oftransformer T1, through switch Q2, resistors Rsense2, RSense1,series-connected switch Q1, and back to the center-tap, and throughinductors L2 a, L1 a to terminal P. During the negative half-cycle,controller 12 turns switch Q2 On and Off to generate the desired DCoutput and provide the desired power factor correction to the AC input.When switch Q2 is On, current flows through the described circuit path(opposite in direction to the circuit path described with respect toFIG. 1A). When switch Q2 is Off, the circuit path is broken and nocurrent flows, except for that current flowing in the secondary windingof transformer T1.

The modulation of switch Q2 is illustrated by voltage waveform 22 shownadjacent to switch Q2, with the negative half-cycle being modulated asindicated into a plurality of pulses. The modulation of switch Q2results in significant common-mode voltages being provided onto thecenter-tap of transformer T1 as common-mode EMI, as illustrated byvoltage waveform 24 shown adjacent to the nodes on either side ofcapacitor C3. The series-connection of switch Q1 results in switch Q1operating as a synchronous rectifier (i.e., diode) that preventscommon-mode EMI from being propagated across switch Q1, as evidence byvoltage waveform 26 shown adjacent to switch Q1. Despite the reversal ofthe current path, the connection of the junction between capacitors C1,C2 to the source of switches Q1, Q2 provides a two-pole filter, in whicha shunt connection between junction of the capacitors and the source ofswitch Q2 provides filtering of the common-mode EMI.

Controller 12 regulates the DC output voltage V0 based, at least inpart, on the monitored input voltage and the monitored current. Abenefit of the series connection of switches Q1 and Q2 is that senseresistors Rsense1 and Rsense2 can be used to monitor the current (oftenreferred to with respect to power supplies as IS sense). In theembodiment shown in FIGS. 1A and 1B, controller 12 employs differentialcurrent sensing to monitor the current. For example, during the positivehalf-cycle, the voltage monitored at input S1 is positive with respectto the common node and the voltage at input S2. During the negativehalf-cycle, the voltage monitored at input S2 is positive with respectto the common node and the voltage at input S1. The difference betweenthe voltage monitored at input S1 and S2 (i.e., absolute value of thedifference) represents the current.

Similarly, differential sensing is employed to monitor the inputvoltage, with controller 12 monitoring the difference in voltage acrosscapacitor C3. Applying the AC input voltage to the center-tap oftransformer T1 results in one-half of the voltage being applied toeither side of capacitor C3 as illustrated by waveforms 18 and 24 shownwith respect to the center-tap position across capacitor C3 in FIGS. 1Aand 1B, respectively. The sum of the voltages provided to inputs VinAand VinB of controller 12 represents the magnitude of the AC inputvoltage Vin. In other embodiments, sensing of the AC input voltage isprovided by monitoring the voltage through either switch Q1 or Q2.However, this requires decision-making regarding which voltage tomonitor because one of the voltages is near zero during each half-cycleof the input voltage. The benefit of summing the voltages on both sidesof capacitor C3 is that the sum will equal the magnitude of the AC inputvoltage, without requiring decision-making. In addition, in theembodiment shown in FIGS. 1A, 1B, in which tertiary winding 14 powerscontroller 12, resistors R1, R2 provide the impedance required formonitoring of the voltage, while also serving to supply start-up powerto controller 12 (used to charge capacitor C4) until tertiary winding 14is able to supply the power required by controller 12.

Diodes D3, D4, capacitor C5, Zener diode Z1, and resistors R3, R4 form acenter-tapped snubber circuit used to protect against transientovervoltage conditions associated with transformer T1. In otherembodiments, the center-tapped snubber circuit may be replaced with abridged snubber circuit that includes two additional diodes connected toform a bridge with diodes D3 and D4.

In this way, power supply 10 offers the efficiency of a bridgeless powersupply, while providing a solution to the EMI filtering problemsassociated with typical bridgeless power supplies. In addition, abenefit of the common node provided by the present invention is itprovides a general purpose connection point equivalent to the AC inputneutral line N. The common node can be connected to transformer shields,heat sinks, etc. to help simplify EMI management and PC board layoutplanning.

FIG. 2 is a circuit diagram of bridgeless PFC boost regulator powersupply 20 according to an embodiment of the present invention. Similarto power supply 10 described with respect to FIGS. 1A and 1B, powersupply 20 converts an AC input voltage to a DC output voltage. Insteadof employing a flyback configuration, however, power supply 20 employs aboost regulator topology in which the center-tapped transformer isreplaced by center-tapped inductor L5. Diodes D5, D6, D7 and D8 rectifythe output of center-tapped inductor L5 to provide a DC output voltage.

In the embodiment shown in FIG. 2, AC input voltage Vin is once againprovided at input terminals P and N. Input terminal P is connected viainductors L3 a, L4 a to a first center-tap position of center-tappedinductor L5. Input terminal N is connected via inductors L3 b, L4 b to asecond center-tap position of inductor L5. Similar to the bifurcation ofthe primary winding of center-tapped transformer T1 discussed withrespect to FIGS. 1A, 1B, inductor L5 is bifurcated into first and secondwinding portions, with capacitor C9 connected between the first andsecond winding portions. Capacitors C7, C8 are connected in series withone another between the AC input terminals and the junction betweencapacitors C7, C8 provides a connection to the common node.

The ends of inductor L5 are connected to respective switches Q3, Q4. Inthe embodiment shown in FIG. 2, switches Q3, Q4 are once again MOSFETshaving a drain, a source, and a gate corresponding with first and secondcontrolled terminals and a control terminal. As discussed above, inother embodiments the MOSFETs may be replaced with other types ofwell-known switching devices. In the embodiment shown in FIG. 2, thedrains of switches Q3, Q4 are connected to the respective distal ends ofcenter-tapped inductor L5. Controller 22 provides drive signals to thegates of switches Q3, Q4 to control whether the switches are On or Off,and the sources of switches Q3, Q4 are connected together via senseresistors Rsense3, Rsense4. In this way, switches Q3, Q4 are connectedin series with one another.

During operation as a boost converter, switches Q3, Q4 are turned On andOff to alternatively charge/discharge inductor L5. When switches Q3, Q4are On a circuit path including series-connected switches Q3, Q4 iscreated that causes energy to be stored in inductor L5. When switchesQ3, Q4 are Off, the circuit path including series-connected switches Q3,Q4 is broken, and inductor L5 discharges stored energy through diodes D5or D8 (providing the desired rectification of the signal) to DC outputVo. Diodes D6 and D7 prevent unwanted core saturation during start upand other transient conditions wherein the AC input voltage Vin exceedsthe DC output Vout.

During the positive half-cycle of AC input voltage Vin, the voltage atterminal P is positive relative to the voltage at terminal N. Currentflows from terminal P, through inductors L3 a, L4 a to the center-tapposition of inductor L5, through switch Q3, sense resistors Rsense3,Resense4, series-connected switch Q4, to the center-tap of inductor L5,and through inductors L4 b, L3 b to terminal N. During the positivehalf-cycle, the state of switch Q3 determines the whether current flowsin the circuit path as described. The modulation of switch Q3 providesthe desired boost conversion of the AC input voltage, but also providessignificant common-mode voltage onto the center-tap of inductor L5.Switch Q4 acts as a synchronous rectifier due to the presence of thebody diode between the source and drain of the device, and preventscommon-mode voltage from being propagated across switch Q4. However,this still leaves significant common-mode voltage at the center-tapposition of inductor L5.

The common-mode voltage provided at the center-tap of inductor L5 isfiltered by connecting the source of switches Q3, Q4 to the junctionbetween capacitors C7, C8. The low-resistance path created by switch Q4between the common node and the AC input terminal N, and the connectionof the common node to the junction between capacitors C7, C8 results inthe voltage between input terminal N and the junction between capacitorsC7, C8 being very small. As a result, common-mode EMI is shunted fromthe junction of capacitors C7, C8 to the source of switch Q3, withcapacitors C7, C8 and inductors L4 a, L4 b providing a first stagetwo-pole filter.

During the negative half-cycle of AC input voltage Vin, the voltage atterminal N is positive relative to the voltage at terminal P. Thedirection of the current is reversed, and switch Q4 now determineswhether the circuit path is closed or open. Modulation provided byswitch Q4 results in common-mode voltage once again being provided intothe center-tap position of inductor L5. Switch Q3 acts as a synchronousrectifier due to the body diode between the source and drain of switchQ4, and prevents common-mode voltage from being propagated onto switchQ3. However, this still leaves significant common-mode voltage at thecenter-tap position of inductor L5.

The common-mode voltage provided at the common-mode of inductor L5 isfiltered by connecting the sources of switches Q3, Q4 to the junctionbetween capacitors C7, C8. The low-resistance path created by switch Q3between the common node and the AC input terminal P, and the connectionof the common node to the junction between capacitors C7, C8 results inthe voltage between input terminal N and the junction between capacitorsC7, C8 being very small. As a result, common-mode EMI is shunted fromthe junction of capacitors C7, C8 to the source of switch Q4, withcapacitors C7, C8 and inductors L4 a, L4 b providing a first stagetwo-pole filter.

Controller 22 provides regulation of the DC output Vo and power factorcorrection based, at least in part, on the monitored input voltage andthe monitored current. As described with respect to the embodiment shownin FIGS. 1A, 1 b, sense resistors Rsense3 and Rsense4 are employed toprovide differential monitoring of the input current (often referred towith respect to power supplies as IS sense). Similarly, differentialsensing is employed to monitor the input voltage, with controller 22monitoring the difference in voltage across capacitor C9 via resistorsR5, R6. In addition, in the embodiment shown in FIGS. 1A, 1B, in whichtertiary winding 24 powers controller 22, resistors R5, R6 provide theimpedance required for monitoring of the voltage, while also serving tosupply start-up power to controller 22 (used to charge capacitor C11)until tertiary winding 24 is able to supply the power required bycontroller 12.

While the invention has been described with reference to an exemplaryembodiment(s), it will be understood by those skilled in the art thatvarious changes may be made and equivalents may be substituted forelements thereof without departing from the scope of the invention. Inaddition, many modifications may be made to adapt a particular situationor material to the teachings of the invention without departing from theessential scope thereof. Therefore, it is intended that the inventionnot be limited to the particular embodiment(s) disclosed, but that theinvention will include all embodiments falling within the scope of theappended claims.

The invention claimed is:
 1. A series-switch bridgeless power supplycomprising: first and second terminals for receiving an alternatingcurrent (AC) input; a first and second capacitor connected in serieswith one another between the first and second terminals, a firstjunction being defined between the first and second capacitor; acenter-tapped inductive device bifurcated into a first winding and asecond winding, the first winding having a first end and a second end,the first end connected to the first terminal at a first center-tapposition of the inductive device, the second winding having a first endand a second end, the first end connected to the second terminal at asecond center-tap position of the inductive device; a third capacitorconnected between the first and second center-tap positions of theinductive device; a first switch having a control terminal and first andsecond controlled terminals, the first controlled terminal electricallyconnected to the second end of the first winding; a second switch havinga control terminal and first and second controlled terminals, the firstcontrolled terminal connected to the second end of the second windingand the second controlled terminal electrically connected to the secondcontrolled terminal of the first switch; and a controller having firstand second drive outputs connected to the control terminals of the firstand second switches, respectively, to selectively turn the first andsecond switches On and Off to alternatively charge/discharge theinductive device, the first and second switches being connected inseries with one another, wherein the first junction between the firstand second capacitors is connected to the second controlled terminals ofthe first and second switches to filter common-mode voltage.
 2. Thepower supply of claim 1, wherein the center-tapped inductive device is atransformer having a primary winding and a secondary winding, whereinthe primary winding is bifurcated into the first winding and the secondwinding, and the secondary winding includes first and second endsconnected to direct current (DC) output terminals via respective firstand second diodes.
 3. The power supply of claim 1, further including: afirst diode connected to the second end of the first winding and a DCoutput terminal; and a second diode connected to the second end of thesecond winding and the DC output terminal, wherein the first and seconddiodes are connected to rectify and communicate discharged energy fromthe inductive device to the DC output terminal.
 4. The power supply ofclaim 1, wherein the controller drives the first and second switches Onand Off synchronously.
 5. The power supply of claim 1, wherein thecontroller drives the first switch On and Off during a positivehalf-cycle of the AC input and second switch On and Off during anegative half-cycle of the AC input.
 6. The power supply of claim 1,further including: a first inductor connected between the first terminaland the first end of the first winding in the center-tapped inductivedevice; and a second inductor connected between the second terminal andthe first end of the second winding in the center-tapped inductivedevice, the first and second inductors providing in conjunction with thefirst and second capacitors a first stage two-pole filter.
 7. The powersupply of claim 1, further including: a first current sense resistor anda second current sense resistor connected between the second controlledterminal of the first switch and the second controlled terminal of thesecond switch.
 8. The power supply of claim 1, further including: atertiary winding coupled to the center-tapped inductive device to supplypower to the controller based on modulations in current through thefirst and second windings of the center-tapped inductive device.
 9. Aseries-switch, bridgeless power supply comprising: first and secondinput terminals for receiving an alternating current (AC) input; a firstand second capacitor connected in series with one another between thefirst and second terminals, a first junction being defined between thefirst and second capacitor; a center-tapped transformer having a primarywinding and a secondary winding, the primary winding bifurcated into afirst winding and a second winding; a first switch having a controlterminal and first and second controlled terminals, the first controlledterminal connected to the first winding; a second switch having acontrol terminal and first and second controlled terminals, the firstcontrolled terminal connected to the second winding and the secondcontrolled terminal connected to the second controlled terminal of thefirst switch; and a controller having first and second drive outputsconnected to the control terminals of the first and second switches,respectively, to selectively turn the first and second switches On andOff to alternatively charge/discharge the primary winding to transferenergy to the secondary winding of the transformer, wherein the firstand second switches are controlled to create a first circuit path fromthe first input terminal, through the first winding of the inductivedevice, the first switch, the second switch, the second winding of theinductive device, and to the second input terminal, the secondcontrolled terminals of the first and second switches being connected tothe junction between the first and second capacitors to provide a filterfor filtering common-mode voltage at the center-tap position of theinductive device.
 10. The power supply of claim 9, wherein thecontroller drives the first and second switches On and Offsynchronously.
 11. The power supply of claim 9, wherein the controllerdrives the first switch On and Off during a positive half-cycle of theAC input and second switch On and Off during a negative half-cycle ofthe AC input.
 12. The power supply of claim 9, further including: afirst inductor connected between the first terminal and the firstwinding in the center-tapped transformer; and a second inductorconnected between the second terminal and the second winding in thecenter-tapped transformer, the first and second inductors providing inconjunction with the first and second capacitors a first stage two-polefilter.
 13. The power supply of claim 9, further including: a firstcurrent sense resistor and a second current sense resistor connectedbetween the second controlled terminal of the first switch and thesecond controlled terminal of the second switch, wherein the controllermonitors current in the power supply based on voltage measured acrossthe first current sense resistor and the second current sense resistor.14. The power supply of claim 9, further including: a tertiary windingcoupled to the center-tapped inductive device to supply power to thecontroller based on modulations in current through the first and secondwindings of the center-tapped inductive device.